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19-2135; Rev 1; 8/02
315MHz Low-Power, +3V Superheterodyne Receiver
General Description
The MAX1470 is a fully integrated low-power CMOS superheterodyne receiver for use with amplitude-shiftkeyed (ASK) data in the 315MHz band. With few required external components, and a low-current power-down mode, it is ideal for cost- and power-sensitive applications in the automotive and consumer markets. The chip consists of a 315MHz low-noise amplifier (LNA), an image rejection mixer, a fully integrated 315MHz phase-lock-loop (PLL), a 10.7MHz IF limiting amplifier stage with received-signal-strength indicator (RSSI) and an ASK demodulator, and analog baseband data-recovery circuitry. The MAX1470 is available in a 28-pin TSSOP package. o Built-In 53dB RF Image Rejection o -115dBm Receive Sensitivity* o 250s Startup Time o Low 5.5mA Operating Supply Current o 1.25A Low-Current Power-Down Mode for Efficient Power Cycling o 250MHz to 500MHz Operating Band (Image Rejection Optimized at 315MHz) o Integrated PLL with On-Board Voltage-Controlled Oscillator (VCO) and Loop Filter o Selectable IF Bandwidth Through External Filter o Complete Receive System from RF to Digital Data Out
*See Note 2, AC Electrical Characteristics.
Features
o Operates from a Single +3.0V to +3.6V Supply
MAX1470
Applications
Remote Keyless Entry Garage Door Openers Remote Controls Wireless Sensors Wireless Computer Peripherals Security Systems Toys Video Game Controllers Medical Systems
Ordering Information
PART MAX1470EUI TEMP RANGE -40C to +85C PIN-PACKAGE 28 TSSOP
Typical Application Circuit appears at end of data sheet. Pin Configuration appears at end of data sheet.
Functional Diagram
LNAOUT 6 MIXIN1 8 MIXIN2 9 MIXOUT 12 IFIN1 17 IFIN2 18 IF LIMITING AMPS LNA 0 Q
LNAIN
3
MAX1470
4
LNASRC
90 I 14 DIVIDE BY 64
RSSI
DVDD
VCO DATA FILTER
AVDD
2,7 PHASE DETECTOR 13 CRYSTAL DRIVER SHUTDOWN DATA SLICER PEAK DETECTOR 1 XTAL1 28 XTAL2 27 PWRDN 25 DATAOUT 20 DSN 19 DSP 26 PDOUT 21 OPP LOOP FILTER
RDF2 100k
RDF1 100k
DGND
AGND
5,10
22 DF
________________________________________________________________ Maxim Integrated Products
1
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at 1-888-629-4642, or visit Maxim's website at www.maxim-ic.com.
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
ABSOLUTE MAXIMUM RATINGS
AVDD to AGND ......................................................-0.3V to +4.0V DVDD to DGND......................................................-0.3V to +4.0V All Other Pins Referenced to AGND...........-0.3V to (VDD + 0.3V) Continuous Power Dissipation (TA = +70C) 28-Pin TSSOP (derate 13mW/C above +70C) .........1039mW Operating Temperature Range MAX1470EUI ...................................................-40C to +85C Storage Temperature Range .............................-60C to +150C Lead Temperature (soldering, 10s) .................................+300C
Stresses beyond those listed under "Absolute Maximum Ratings" may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
DC ELECTRICAL CHARACTERISTICS
(Typical Application Circuit, VDD = +3.0V to +3.6V, no RF signal applied, TA = -40C to +85C. Typical values are at VDD = +3.3V, TA = +25C, unless otherwise noted.) (Note 1)
PARAMETER Supply Voltage Supply Current Shutdown Supply Current PWRDN Voltage Input Low PWRDN Voltage Input High DATAOUT Voltage Output Low DATAOUT Voltage Output High SYMBOL VDD IDD ISHUTDOWN VIL VIH VOL VOH IDATAOUT = 100A IDATAOUT = -100A VDD 0.4 VDD 0.4 0.4 PWRDN = VDD PWRDN = GND CONDITIONS MIN 3.0 5.5 1.25 0.4 TYP MAX 3.6 UNITS V mA A V V V V
AC ELECTRICAL CHARACTERISTICS
(Typical Application Circuit, all RF inputs and outputs are referenced to 50, VDD = +3.3V, TA = +25C, fRFIN = 315MHz, unless otherwise noted.) (Note 1)
PARAMETER GENERAL CHARACTERISTICS Maximum Startup Time Maximum Receiver Input Level Minimum Receiver Input Level, 315MHz Minimum Receiver Input Level, 433.92MHz Receivers LOW-NOISE AMPLIFIER (LNA) Input Impedance 1dB Compression Point Input-Referred 3rd-Order Intercept LO Signal Feedthrough to Antenna Output Impedance S22LNA Normalized to 50 S11LNA P1dBLNA IIP3LNA Normalized to 50 (Note 3) 1 - j4 -22 -18 -95 0.12 j4.4 dBm dBm dBm fRFIN TON RFINMAX RFINMIN Time from PWRDN deasserting to valid data out Modulation depth 60dB Average carrier power level (Note 2) Peak power level (Note 2) Average carrier power level (Note 2) Peak power level (Note 2) 250 0 -115 -109 -110 -104 250 to 500 s dBm dBm dBm MHz SYMBOL CONDITIONS MIN TYP MAX UNITS
2
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315MHz Low-Power, +3V Superheterodyne Receiver
AC ELECTRICAL CHARACTERISTICS (continued)
(Typical Application Circuit, all RF inputs and outputs are referenced to 50, VDD = +3.3V, TA = +25C, fRFIN = 315MHz, unless otherwise noted.) (Note 1)
PARAMETER Noise Figure Power Gain MIXER Input Impedance Input-Referred 3rd-Order Intercept Output Impedance Image Rejection Noise Figure Conversion Gain Input Impedance Operating Frequency RSSI Linearity RSSI Dynamic Range RSSI Level DATA FILTER Maximum Bandwidth DATA SLICER Comparator Bandwidth Maximum Load Capacitance CRYSTAL OSCILLATOR Reference Frequency fREF 4.7547 MHz BWCMP CLOAD 100 10 kHz pF BWDF 100 kHz PRFIN < -120dBm PRFIN > -50dBm ZIN_IF fIF NFMIX 330 IF filter load S11MIX IIP3MIX ZOUT_MIX fRFIN = 315MHz, fRF_IMAGE = 293.6MHz (Note 4) fRFIN = 433.92MHz, fRF_IMAGE = 412.52MHz 40 Normalized to 50 0.25 j2.4 -18 330 53 39 16 13 330 10.7 1 65 1.2 2.0 dBm dB dB dB MHz dB dB V SYMBOL NFLNA CONDITIONS MIN TYP 2.0 16 MAX UNITS dB dB
MAX1470
INTERMEDIATE-FREQUENCY DEMODULATOR BLOCK
Note 1: Parts are production tested at TA = +25C; Min and Max values are guaranteed by design and characterization. Note 2: BER = 2E-3, Manchester encoded, data rate = 4kbps, IF bandwidth = 350kHz. Note 3: Input impedance is measured at the LNAIN pin. Note that the impedance includes the 15nH inductive degeneration connected from the LNASRC. Note 4: Guaranteed by production test.
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3
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
Typical Operating Characteristics
(VDD = +3.3V, TA = +25C, unless otherwise noted. Typical Application Circuit.)
SUPPLY CURRENT vs. SUPPLY VOLTAGE
MAX1470 toc01
BIT-ERROR RATE vs. AVERAGE RF INPUT POWER
MAX1470 toc02
RSSI vs. AVERAGE RF INPUT POWER
IF BANDWIDTH = 350kHz 2.0 1.8
MAX1470 toc03
6.1 5.9 SUPPLY CURRENT (mA) 5.7 5.5 5.3 5.1 4.9 4.7 2.7 2.9 3.1 3.3 3.5 SUPPLY VOLTAGE (V) TA = -40C TA = +25C TA = +85C
10
2.2
BIT-ERROR RATE (%)
1
RSSI (V) -120 -118 -116 -114
1.6 1.4 1.2
0.1 AVERAGE RF INPUT POWER (dBm)
1.0 -140 -120 -100 -80 -60 -40 -20 AVERAGE RF INPUT POWER (dBm)
RECEIVER SENSITIVITY vs. TEMPERATURE
MAX1470 toc04
IMAGE REJECTION vs. TEMPERATURE
MAX1470 toc05
SYSTEM GAIN vs. IF FREQUENCY
FROM RFIN TO MIXOUT fLO = 304.3MHz UPPER SIDEBAND SYSTEM GAIN (dB)
MAX1470 toc06
-116.0 AVERAGE RF INPUT POWER 1% BER IF BANDWIDTH = 350kHz -116.5
60
60 50 40 30 20 10 0 LOWER SIDEBAND 53dB IMAGE REJECTION
RECEIVER SENSITIVITY (dBm)
IMAGE REJECTION (dB)
55
-117.0
50
-117.5
-118.0 -40 -20 0 20 40 60 80 TEMPERATURE (C)
45 -40 -20 0 20 40 60 80 TEMPERATURE (C)
-10 0 10 20 30 IF FREQUENCY (MHz) 40
LNA GAIN vs. RF FREQUENCY
MAX1470 toc07
SUPPLY CURRENT vs. LO FREQUENCY
MAX1470 toc08
INPUT IMPEDANCE vs. INDUCTIVE DEGENERATION
70 60
REAL IMPEDANCE ()
MAX1470 toc09
30 LC TANK FILTER TUNED TO 315MHz 25 LNA GAIN (dB)
7.2 6.7 SUPPLY CURRENT (mA) 6.2 5.7 5.2 4.7
0 -50
50 40 30 20 10 0
REAL IMPEDANCE
-100 -150 -200 -250
20
15
IMAGINARY IMPEDANCE
-300 -350
10 250 275 300 325 350 375 RF FREQUENCY (MHz)
4.2 150 200 250 300 350 400 450 500 LO FREQUENCY (MHz)
1
10 INDUCTIVE DEGENERATION (nH)
100
4
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IMAGINARY IMPEDANCE ()
315MHz Low-Power, +3V Superheterodyne Receiver
Typical Operating Characteristics (continued)
(VDD = +3.3V, TA = +25C, unless otherwise noted. Typical Application Circuit.)
NORMALIZED IF GAIN vs. IF FREQUENCY
MAX1470 toc10
MAX1470
IMAGE REJECTION vs. RF FREQUENCY
MAX1470 toc11
5 3dB BANDWIDTH = 11.7MHz NORMALIZED IF GAIN (dB) 0
60
-5
IMAGE REJECTION (dB) 1 10 IF FREQUENCY (MHz) 100
50
40
-10
-15
30
-20
20 150 200 250 300 350 400 450 500 RF FREQUENCY (MHz)
S11 MAGNITUDE-LOG PLOT OF RFIN
MAX1470 toc12
S11 SMITH PLOT OF RFIN
MAX1470 toc13
0dB
315MHz
10dB/ div 315MHz, -29.5dB
50MHz
1GHz 50MHz 1GHz
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5
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
Pin Description
PIN 1 2, 7 3 4 5, 10 6 8 9 11, 15, 16, 23, 24 12 13 14 17 18 19 20 21 22 25 26 27 28 NAME XTAL1 AVDD LNAIN LNASRC AGND LNAOUT MIXIN1 MIXIN2 I.C. MIXOUT DGND DVDD IFIN1 IFIN2 DSP DSN OPP DF DATAOUT PDOUT PWRDN XTAL2 1st Crystal Input Positive Analog Supply Voltage for RF Sections. Decouple to AGND with 0.01F capacitors. Low-Noise Amplifier Input Low-Noise Amplifier Source. Connect inductor to ground to set LNA input impedance (see LowNoise Amplifier section). Analog Ground Low-Noise Amplifier Output 1st Differential Mixer Input. Must be AC-coupled to driving input. 2nd Differential Mixer Input. Must be AC-coupled to driving input. Internally Connected. Do not make connection to these pins. 330 Mixer Output Digital Ground Positive Digital Supply Voltage. Decouple to DGND with a 0.01F capacitor. 1st Differential Intermediate Frequency Limiter Amplifier Input 2nd Differential Intermediate Frequency Limiter Amplifier Input Positive Data Slicer Input Negative Data Slicer Input Noninverting Op Amp. Input for the Sallen-Key data filter. Data Filter Feedback Node. Input for the feedback of the Sallen-Key data filter. Digital Baseband Data Output Peak Detector Output Power-Down Select Input. Drive this pin with a logic low to shut down the IC. 2nd Crystal Input FUNCTION
Detailed Description
The MAX1470 CMOS superheterodyne receiver and a few external components provide the complete receive chain from the antenna to the digital output data. Depending on signal power and component selection, data rates as high as 100kbps can be achieved. The MAX1470 is designed to receive binary ASK data on a 315MHz carrier. ASK modulation uses a difference in amplitude of the carrier to represent logic 0 and logic 1 data.
and the LC tank network between the LNA output and the mixer inputs. The off-chip inductive degeneration is achieved by connecting an inductor from LNASRC to AGND. This inductor sets the real part of the input impedance at LNAIN, allowing for a more flexible match for low-input impedance such as a PC board trace antenna. A nominal value for this inductor with a 50 input impedance is 15nH, but is affected by PC board trace. See Typical Operating Characteristics for the relationship between the inductance and input impedance. The LC tank filter connected to LNAOUT comprises L1 and C9 (see Typical Applications Circuit). L1 and C9 values are selected to resonate at the RF input frequency of 315MHz. The resonant frequency is given by:
Low-Noise Amplifier
The LNA is a cascode amplifier with off-chip inductive degeneration that achieves approximately 16dB of power gain with a 2.0dB noise figure and an IIP3 of -18dBm. The gain and noise figure is dependent on both the antenna matching network at the LNA input,
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315MHz Low-Power, +3V Superheterodyne Receiver
= 1 2 L TOTAL x CTOTAL To allow the smallest possible IF bandwidth (for best sensitivity), the tolerance of the reference must be minimized.
MAX1470
Intermediate Frequency
where: L TOTAL = L1+ LPARASITICS CTOTAL = C9 + CPARASITICS LPARASITICS and CPARASITICS include inductance and capacitance of the PC board traces, package pins, mixer input impedance, LNA output impedance, etc. These parasitics at high frequencies cannot be ignored and can have a dramatic effect on the tank filter center frequency. Lab experimentation should be done to optimize the center frequency of the tank. The IF section presents a differential 330 load to provide matching for the off-chip ceramic filter. The internal five AC-coupled limiting amplifiers produce an overall gain of approximately 65dB, with a bandpass-filter-type response centered near the 10.7MHz IF frequency with a 3dB bandwidth of approximately 11.5MHz. The RSSI circuit demodulates the IF to baseband by producing a DC output proportional to the log of the IF signal level with a slope of approximately 15mV/dB (see Typical Operating Characteristics).
Applications Information
Crystal Oscillator
The XTAL oscillator in the MAX1470 is designed to present a capacitance of approximately 3pF between XTAL1 and XTAL2. If a crystal designed to oscillate with a different load capacitance is used, the crystal is pulled away from its stated operating frequency, introducing an error in the reference frequency. Crystals designed to operate with higher differential load capacitance always pull the reference frequency higher. For example, a 4.7547MHz crystal designed to operate with a 10pF load capacitance oscillates at 4.7563MHz with the MAX1470, causing the receiver to be tuned to 315.1MHz rather than 315.0MHz, an error of about 100kHz, or 320ppm. In actuality, the oscillator pulls every crystal. The crystal's natural frequency is really below its specified frequency, but when loaded with the specified load capacitance, the crystal is pulled and oscillates at its specified frequency. This pulling is already accounted for in the specification of the load capacitance. Additional pulling can be calculated if the electrical parameters of the crystal are known. The frequency pulling is given by: p = Cm 1 1 6 - x 10 2 Ccase + Cload Ccase + Cspec
Mixer
A unique feature of the MAX1470 is the integrated image rejection of the mixer. This device was designed to eliminate the need for a costly front-end SAW filter for many applications. The advantage of not using a SAW filter is increased sensitivity, simplified antenna matching, less board space, and lower cost. The mixer cell is a pair of double-balanced mixers that perform an IQ downconversion of the 315MHz RF input to the 10.7MHz IF with low-side injection (i.e., fLO = fRF - fIF). The image rejection circuit then combines these signals to achieve ~50dB of image rejection over the full temperature range. Low-side injection is required due to the on-chip image-rejection architecture. The IF output is driven by a source-follower, biased to create a driving impedance of 330 to interface with an off-chip 330 ceramic IF filter. The voltage conversion gain driving a 330 load is approximately 13dB.
Phase-Lock Loop
The PLL block contains a phase detector, charge pump/integrated loop filter, VCO, asynchronous 64x clock divider, and crystal oscillator. This PLL does not require any external components. The quadrature VCO is centered at the nominal LO frequency of 304.3MHz. For an input RF frequency of 315MHz, a reference frequency of 4.7547MHz is needed for a 10.7MHz IF frequency (low-side injection is required). The relationship between the RF, IF, and reference frequencies is given by: fREF = (fRF - fIF) / 64
where: fp is the amount the crystal frequency is pulled in ppm. Cm is the motional capacitance of the crystal. Ccase is the case capacitance. Cspec is the specified load capacitance. Cload is the actual load capacitance.
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7
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
When the crystal is loaded as specified, i.e., Cload = Cspec, the frequency pulling equals zero.
Data Filter
The data filter is implemented as a 2nd-order lowpass Sallen-Key filter. The pole locations are set by the combination of two on-chip resistors and two external capacitors. Adjusting the value of the external capacitors changes the corner frequency to optimize for different data rates. The corner frequency should be set to approximately 1.5 times the fastest expected data rate from the transmitter. Keeping the corner frequency near the data rate rejects any noise at higher frequencies, resulting in an increase in receiver sensitivity. The configuration shown in Figure 1 can create a Butterworth or Bessel response. The Butterworth filter offers a very flat amplitude response in the passband and a roll-off rate of 40dB/decade for the two-pole filter. The Bessel filter has a linear phase response, which works well for filtering digital data. To calculate the value of C5 and C6, use the following equations along with the coefficients in Table 1: C5 = C6 =
MAX1470
RSSI RDF1 100k
RDF2 100k
19 DSP
21 OPP C6
22 DF C5
Figure 1. Sallen-Key Lowpass Data Filter
Choosing standard capacitor values changes C5 to 470pF and C6 to 220pF, as shown in the Typical Application Circuit.
Data Slicer
The purpose of the data slicer is to take the analog output of the data filter and convert it to a digital signal. This is achieved by using a comparator and comparing the analog input to a threshold voltage. The threshold voltage is set by the voltage on DSN, which is connected to the negative input of the data slicer comparator. The positive input is connected to the output of the data filter internally, and also the DSP pin for use with some data slicer configurations. The suggested data slicer configuration uses a resistor (R1) connected between DSN and DSP with a capacitor (C4) from DSN to DGND (Figure 2). This configuration averages the analog output of the filter and sets the threshold to approximately 50% of that amplitude. With this configuration, the threshold automatically adjusts as the analog signal varies, minimizing the possibility for errors in the digital data. The sizes of R1 and C4 affect how fast the threshold tracks the analog amplitude. Be sure to keep the corner frequency of the RC circuit lower than the lowest expected data rate. Note that a long string of zeros or ones can cause the threshold to drift. This configuration works best if a coding scheme, such as Manchester code, which has an equal number of zeros and ones, is used.
a 100k fc 4 100k fc
(
b
)( )( )
(
a
)( )( )
where fC is the desired 3dB corner frequency. For example, to choose a Butterworth filter response with a corner frequency of 5kHz: C5 = C6 =
(1.414)(100k)(3.14)(5kHz) (4)(100k)(3.14)(5kHz)
a 1.414 1.3617
1.000
450pF
1.414
225pF
Table 1. Coefficents to Calculate C5 and C6
FILTER TYPE Butterworth (Q = 0.707) Bessel (Q = 0.577) b 1.000 0.618
Peak Detector
The peak detector output (PDOUT), in conjunction with an external RC filter, creates a DC output voltage equal to the peak value of the data signal. The resistor provides a path for the capacitor to discharge, allowing the
8
_______________________________________________________________________________________
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
MAX1470
DATA FILTER DATA SLICER 25 DATA OUT C4 20 DSN R1 19 DSP
DATA SLICER
MAX1470
DATA FILTER
25 DATA OUT 47nF
20 DSN 25k
19 DSP 250k
26 PDOUT
47nF
Figure 2. Generating Data Slicer Threshold
Figure 3. Using PDOUT for Faster Startup
peak detector to dynamically follow peak changes of the data filter output voltage. For faster receiver startup, the circuit shown in Figure 3 can be used.
Layout Considerations
A properly designed PC board is an essential part of any RF/microwave circuit. On high-frequency inputs and outputs, use controlled-impedance lines and keep them as short as possible to minimize losses and radiation. At high frequencies, trace lengths that are approximately 1/20 the wavelength or longer become antennas. For example, a 2in trace at 315MHz can act as an antenna. Keeping the traces short also reduces parasitic inductance. Generally, 1in of a PC board trace adds about 20nH of parasitic inductance. The parasitic inductance can have a dramatic effect on the effective inductance. For example, a 0.5in trace connecting a 100nH inductor adds an extra 10nH of inductance or 10%. To reduce the parasitic inductance, use wider traces and a solid ground or power plane below the signal traces. Using a solid ground plane can reduce the parasitic inductance from approximately 20nH/in to 7nH/in. Also, use low-inductance connections to ground on all GND pins, and place decoupling capacitors close to all VDD connections.
433.92MHz Band
The MAX1470 can be configured to receive ASK modulated data with carrier frequency ranging from 250MHz to 500MHz. Only a small number of components need to be changed to retune the RF section to the desired RF frequency. Table 2 shows a list of changed components and their values for a 433.92MHz RF; all other components remain unchanged. The integrated image rejection of the MAX1470 is specifically designed to function with a 315MHz input frequency by attenuating any signal at 293.6MHz. The benefit of the on-chip image rejection is that an external SAW filter is not needed, reducing cost and the insertion loss associated with SAW filters. The image rejection cannot be retuned for different RF input frequencies and therefore is degraded. The image rejection at 433.92MHz is typically 39dB.
Table 2. Changed Component Values for 433.92MHz
COMPONENT C9 L1 L2 Y1 VALUE FOR 433MHz RF 1.0pF 15nH 56nH 6.6128MHz
Chip Information
TRANSISTOR COUNT: 1835 PROCESS: CMOS
Note: These values are affected by PC board layout. _______________________________________________________________________________________ 9
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
Typical Application Circuit
+3.3V Y1 4.7547MHz
C12 0.01F ANTENNA (RFIN) 1 XTAL1 XTAL2 28
2 C7 100pF L2 100nH 3 L3 15nH 4
AVDD
PWRDN 27
SHUTDOWN
LNAIN
PDOUT 26
LNASRC
DATAOUT 25
+3.3V
L1 27nH
5
AGND
I.C. 24 DATAOUT
6 C9 2.2pF C11 100pF 8 C2 0.01F 7
LNAOUT
I.C. 23
AVDD
MAX1470
DF 22
MIXIN1
OPP 21 C5 470pF
9 C10 220pF C8 100pF
MIXIN2
DSN 20
10 AGND
DSP 19
11 I.C.
IFIN2 18
C3 1500pF C6 220pF R1 5k C4 0.47F
12 MIXOUT
IFIN1 17
13 DGND
I.C. 16
14 DVDD C1 0.01F U1 10.7MHz
I.C. 15
10
______________________________________________________________________________________
315MHz Low-Power, +3V Superheterodyne Receiver
Pin Configuration
TOP VIEW
XTAL1 1 AVDD 2 LNAIN 3 LNASRC 4 AGND 5 LNAOUT 6 AVDD 7 MIXIN1 8 MIXIN2 9 AGND 10 I.C. 11 MIXOUT 12 DGND 13 DVDD 14 28 XTAL2 27 PWRDN 26 PDOUT 25 DATAOUT 24 I.C.
MAX1470
MAX1470
23 I.C. 22 DF 21 OPP 20 DSN 19 DSP 18 IFIN2 17 IFIN1 16 I.C. 15 I.C.
TSSOP
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11
315MHz Low-Power, +3V Superheterodyne Receiver MAX1470
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to www.maxim-ic.com/packages.)
TSSOP4.40mm.EPS
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
12 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 (c) 2002 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.

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